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general description the MAX17112 is a high-performance, step-up, dc-dc converter that provides a regulated supply voltage for active-matrix thin-film transistor (tft) liquid-crystal dis- plays (lcds). the MAX17112 incorporates current- mode, fixed-frequency (1mhz), pulse-width modulation (pwm) circuitry with a built-in, n-channel power mosfet to achieve high efficiency and fast-transient response. the input overvoltage protection (ovp) function pre- vents damage to the MAX17112 from an input surge voltage (up to 24v). the high switching frequency (1mhz) allows the use of ultra-small inductors and low-esr ceramic capacitors. the current-mode architecture provides fast-transient response to pulsed loads. a compensation pin (comp) gives users flexibility in adjusting loop dynamics. the internal mosfet can generate output voltages up to 20v from an input voltage between 2.6v and 5.5v. soft-start slowly ramps the input current and is pro- grammable with an external capacitor. the MAX17112 is available in a 10-pin tdfn package. applications notebook computer displays lcd monitor panels features input overvoltage protection adjustable output from v in to 20v 2.6v to 5.5v input supply range input supply undervoltage lockout 1mhz fixed switching frequency programmable soft-start small 10-pin, tdfn package thermal-overload protection MAX17112 high-performance, step-up, dc-dc converter ________________________________________________________________ maxim integrated products 1 1 + 3 4 10 8 7 ss in lx comp v l gnd MAX17112 29 shdn fb 56 lx *ep *exposed pad gnd tdfn 3mm 3mm top view pin configuration ordering information lx lx fb gnd gnd gnd v l in comp ss ep 1 4 5 2 3 9 8 67 10 v out v in 2.6v to 5.5v shdn MAX17112 simplified operating circuit for pricing, delivery, and ordering information, please contact maxim direct at 1-888-629-4642, or visit maxim? website at www.maxim-ic.com. evaluation kit available part temp range pin-package MAX17112etb+ -40c to +85c 10 tdfn-ep* + denotes a lead(pb)-free/rohs-compliant package. * ep = exposed pad. 19-4393; rev 0; 12/08
MAX17112 high-performance, step-up, dc-dc converter 2 _______________________________________________________________________________________ absolute maximum ratings electrical characteristics (v l = 3v, t a = 0? to +85?, unless otherwise noted.) stresses beyond those listed under ?bsolute maximum ratings?may cause permanent damage to the device. these are stress rating s only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specificatio ns is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. lx to gnd ..............................................................-0.3v to +24v in to gnd ...............................................................-0.3v to +24v shdn , v l to gnd..................................................-0.3v to +7.5v comp, ss, fb to gnd ..................................-0.3v to (v l + 0.3v) lx switch maximum continuous rms current .....................3.2a continuous power dissipation (t a = +70 c) 10-pin 3mm x 3mm thin tdfn (derate 24.4mw/ c above +70 c) ............................1951mw operating temperature range ...........................-40? to +85 c junction temperature ......................................................+150 c storage temperature range .............................-65? to +150 c lead temperature (soldering, 10s) .................................+300 c parameter conditions min typ max units v out < 18v 2.6 5.5 v in supply range 18v < v out < 20v 4.0 5.5 v ovp threshold v in rising 6.2 6.6 7 v ovp switch resistance 8 12 20 output voltage range 20 v vl undervoltage-lockout threshold v l rising; typical hysteresis is 50mv; lx remains off below this level 2.30 2.45 2.57 v v fb = 1.3v, not switching 0.3 0.6 in quiescent current v fb = 1.0v, switching 1.5 2.5 ma in shutdown supply current shdn = gnd 160 250 a temperature rising 160 thermal shutdown hysteresis 20 c error amplifier feedback voltage level to produce v comp = 1.24v 1.23 1.24 1.25 v fb input bias current v fb = 1.24v 50 125 225 na fb line regulation level to produce v comp = 1.24v, 2.6v < v in < 5.5v 0.05 0.15 %/v transconductance 110 300 450 s voltage gain 2400 v/v shutdown fb input voltage shdn = gnd 0.05 0.10 0.15 v oscillator frequency (f osc ) 800 1000 1200 khz maximum duty cycle 89 92 95 % n-channel mosfet current limit v fb = 1v, 75% duty cycle, v l = 5v 3.9 4.6 5.3 a v l = 5v (typ value at t a = +25c) (note 1) 110 170 on-resistance v l = 3v (typ value at t a = +25c) (note 1) 135 210 m leakage current v lx = 20v 12 25 a current-sense transresistance v l = 5v 0.09 0.15 0.25 v/a
MAX17112 high-performance, step-up, dc-dc converter _______________________________________________________________________________________ 3 parameter conditions min typ max units soft-start reset switch resistance 25 charge current v ss = 1.2v 1.5 3.5 5.5 a control inputs shdn threshold shdn rising 1.1 1.16 1.22 v shdn input hysteresis 60 mv shdn discharge resistance v l < uvlo 20 shdn charge current 4.25 5 5.75 a charge current delay time 80 s electrical characteristics (continued) (v vl = 3v, t a = 0? to +85?, unless otherwise noted.) electrical characteristics (v l = 3v, t a = -40? to +85?, unless otherwise noted.) (note 1) parameter conditions min max units v out < 18v 2.6 5.5 v in supply range 18v < v out < 20v 4.0 5.5 v output voltage range 20 v output switch resistance 8 20 vl undervoltage-lockout threshold v l rising; typical hysteresis is 50mv; lx remains off below this level 2.30 2.57 v v fb = 1.3v, not switching 0.6 in quiescent current v fb = 1.0v, switching 2.5 ma in shutdown supply current shdn = gnd 250 a error amplifier feedback voltage level to produce v comp = 1.24v 1.227 1.253 v fb input bias current v fb = 1.24v 225 na transconductance 110 450 s shutdown fb input voltage shdn = gnd 0.05 0.15 v oscillator frequency (f osc ) 750 1250 khz maximum duty cycle 89 96 %
efficiency vs. load current (v in = 5v, v out = 15v) MAX17112 toc01 load current (ma) efficiency (%) 100 10 60 70 80 90 100 50 1 1000 efficiency vs. load current (v in = 3.3v, v out = 9v) MAX17112 toc02 load current (ma) efficiency (%) 100 10 60 70 80 90 100 50 1 1000 load regulation (v out = 15v) MAX17112 toc03 load current (ma) load regulation (%) 100 10 -0.5 0 0.5 1.0 -1.0 1 1000 v in = 5.0v v in = 3.3v typical operating characteristics (circuit of figure 1, v in = 5v, v main = 15v, t a = +25?, unless otherwise noted.) MAX17112 high-performance, step-up, dc-dc converter 4 _______________________________________________________________________________________ electrical characteristics (continued) (v vl = 3v, t a = -40? to +85?, unless otherwise noted.) (note 1) parameter conditions min max units n-channel mosfet current limit v fb = 1v, 75% duty cycle, v l = 5v 3.9 5.3 a v l = 5v 170 on-resistance v l = 3v 210 m current-sense transresistance v l = 5v 0.09 0.25 v/a soft-start reset switch resistance 25 charge current v ss = 1.2v 1.5 5.5 a control inputs shdn threshold shdn rising 1.19 1.29 v shdn charge current 4.25 5.75 a note 1: limits are 100% production tested at t a = +25?. maximum and minimum limits over temperature are guaranteed by design and characterization.
MAX17112 high-performance, step-up, dc-dc converter _______________________________________________________________________________________ 5 load-transient response (i load = 50ma to 550ma) MAX17112 toc07 100 s/div 50ma 0 15v 0 v out 500mv/div ac-coupled i out 500ma/div inductor current 2a/div l = 2.7 h r comp = 47k c comp1 = 560pf pulsed load-transient response (i load = 100ma to 1.1a) MAX17112 toc08 10 s/div 0.1a 15v 0 v out 200mv/div ac-coupled i out 1a/div inductor current 1a/div l = 2.7 h r comp = 47k c comp1 = 560pf switching waveforms (i load = 600ma) MAX17112 toc09 1 v in ovp protection MAX17112 toc10 10ms/div 0 0 v in 5v/div v l 5v/div typical operating characteristics (continued) (circuit of figure 1, v in = 5v, v main = 15v, t a = +25?, unless otherwise noted.) switching frequency vs. input voltage MAX17112 toc04 input voltage (v) switching frequency (khz) 4.5 3.5 1000 1100 900 2.5 5.5 4.0 3.0 5.0 supply current vs. supply voltage MAX17112 toc05 supply voltage (v) supply current (ma) 4.5 3.5 2.0 1.5 1.0 0.5 4.0 3.5 3.0 2.5 0 2.5 5.5 4.0 3.0 5.0 switching nonswitching soft-start (r load = 30 ) MAX17112 toc06 2ms/div 0 0 v out 5v/div inductor current 1a/div
MAX17112 high-performance, step-up, dc-dc converter 6 _______________________________________________________________________________________ pin description pin name function 1 comp compensation pin for error amplifier. connect a series rc from comp to ground. typical values are 47k and 580pf. 2 fb feedback. the fb regulation voltage is 1.24v nominal. connect an external resistor-divider center tap here and minimize the trace area. set v out according to the output voltage selection section. 3 v l ic supply. there is an internal switch between in and v l and the switch disconnects when an overvoltage condition on in is detected. bypass v l to gnd with a 1f capacitor. 4, 5 gnd ground 6, 7 lx switch. lx is the drain of the internal mosfet. 8 in supply voltage input. bypass in with a minimum 1f ceramic capacitor directly to gnd. 9 shdn shutdown control input. drive shdn high to turn on the MAX17112 for normal operation. connect a capacitor to the shdn pin to create a delayed turn-on. the time delay is 0.25 x c (typ), c in microfarads. shdn can be driven from a logic signal directly, in which case a resistor is required in series with shdn . 10 ss soft-start control. connect a soft-start capacitor (c ss ). leave open for no soft-start. the soft-start capacitor is charged at a rate of 4a/c ss . ep exposed pad. connect to gnd. fb gnd gnd gnd ep in comp 1 4 5 lx 7 lx 6 2 8 v out +15v/600ma v in 4.5v to 5.5v MAX17112 c2 4.7 f 10v c1 4.7 f 10v c3 1 f c10 1 f c9 1 f c4 3.3nf c5 560pf c6 open l1 2.7 h d1 r2 47k r3 20k r4 221k c7 10 f 25v c8 10 f 25v v l ss 3 9 10 shdn u1 figure 1. typical operating circuit
detailed description the MAX17112 is a highly efficient, power-management ic that employs a current-mode, fixed-frequency, pwm architecture for fast-transient response and low-noise operation. the high switching frequency (1mhz) allows the use of ultra-small inductors and low-esr ceramic capacitors. the current-mode architecture provides fast- transient response to pulsed loads. a compensation pin (comp) gives users flexibility in adjusting loop dynam- ics. the internal mosfet can generate output voltages up to 20v from a 2.6v to 5.5v input voltage. the soft- start function slowly ramps the input current and is pro- grammable with an external capacitor. the input overvoltage protection function prevents damage to the MAX17112 from input surge voltages up to 24v. the error amplifier compares the signal at fb to 1.24v and varies the comp output. the voltage at comp determines the current trip point each time the internal mosfet turns on. as the load changes, the error amplifier sources or sinks current to the comp output to command the inductor peak current necessary to service the load. to maintain stability at high duty cycles, a slope compensation signal is summed with the current-sense signal. at light loads, this architecture allows the device to skip cycles to prevent overcharg- ing the output capacitors. MAX17112 high-performance, step-up, dc-dc converter _______________________________________________________________________________________ 7 1.2mhz oscillator 1.24v fb ss 4 a soft-start shdn lx v main current sense gnd comp clock ovp error amplifier pwm comparator slope compensation ic supply voltage logic and driver in v in v l shutdown figure 2. functional diagram
MAX17112 high-performance, step-up, dc-dc converter 8 _______________________________________________________________________________________ output current capability the output current capability of the MAX17112 is a function of current limit, input voltage, operating fre- quency, and inductor value. because of the slope com- pensation used to stabilize the feedback loop, the inductor current limit depends on the duty cycle. the current limit is determined by the following equation: where i lim_ec is the current limit specified at 75% duty cycle (see the electrical characteristics table) and d is the duty cycle. the output current capability depends on the current- limit value and is governed by the following equation: where i lim is the current limit calculated above, is the regulator efficiency (85% nominal), d is the duty cycle, and f osc is switching frequency. the duty cycle when operating at the current limit is: where v diode is the rectifier diode forward voltage and r on is the on-resistance of the internal mosfet. soft-start the MAX17112 can be programmed for soft-start upon power-up with an external capacitor. when the shut- down pin is taken high, the soft-start capacitor (c ss ) is immediately charged to 0.4v. then the capacitor is charged at a constant current of 4a (typ). during this time, the ss voltage directly controls the peak inductor current period. full current limit is readied at v ss = 1.5v. the maximum load current is available after the soft- start is completed. when shdn is low, ss is discharged to ground. overvoltage protection (ovp) to prevent damage due to an input surge voltage, the MAX17112 integrates an ovp circuit. there is an internal switch between in and v l , which is on when the in volt- age is less than 6.6v (typ). the switch is off when the in exceeds 6.6v (typ). since v l supplies the ic, the switch protects the ic from damage when excessively high voltage is applied to in. v l undervoltage lockout (uvlo) the undervoltage lockout (uvlo) circuit compares the voltage at v l with the uvlo (2.45v typ) to ensure that the input voltage is high enough for reliable operation. the 50mv (typ) hysteresis prevents supply transients from causing a restart. once the v l voltage exceeds the uvlo-rising threshold, the startup begins. when the input voltage falls below the uvlo-falling threshold, the main step-up regulator turns off. startup using shdn the MAX17112 can be enabled by applying high volt- age on the shdn pin. figure 2 shows the block dia- gram of the internal shdn pin function. there are two ways to apply this high voltage. when shdn is con- nected to an external capacitor, an internal 5a current source charges up this capacitor and when the voltage on shdn passes 1.24v, the ic starts up. another way to enable the ic through the shdn pin is to directly apply a logic-high signal to shdn instead of connect- ing a capacitor. the delay time for startup by connecting an external capacitor at shdn can be estimated using the follow- ing equation: where c shdn is in microfarads. when enabling the ic by applying a logic-high signal to shdn , a series resistor should be inserted between the logic signal and shdn for protection purposes. this resistor can help limit the current drawn from the logic signal supply into the shdn pin when shdn is dis- charged to gnd through the internal switch at the moment of startup when v l < uvlo. a typical value for this resistor is 10k . figure 3 shows the application cir- cuit for this enabling method of applying a logic-high signal to shdn through a 10k resistor. t v a cc delay = ? 124 5 025 . . shdn shdn d vvv virv out in diode out lim on diode = + + - - i v v out max in ou () = ? ? ? ? ? ? i- 0.5 d v fl lim in osc tt i = (1.26 - 0.35 d) i lim lim_ec
MAX17112 high-performance, step-up, dc-dc converter _______________________________________________________________________________________ 9 applications information step-up regulators using the MAX17112 can be designed by performing simple calculations for a first iteration. all designs should be prototyped and tested prior to production. table 1 provides a list of power components for the typical applications circuit. table 2 lists component suppliers. the choice of external components is primarily dictated by output voltage, maximum load current, and maxi- mum and minimum input voltages. begin by selecting an inductor value. once the inductance is known, choose the diode and capacitors. inductor selection the minimum inductance value, peak current rating, and series resistance are factors to consider when selecting the inductor. these factors influence the con- verter? efficiency, maximum output load capability, transient response time, and output voltage ripple. physical size and cost are also important factors to be considered. fb gnd gnd gnd ep in comp 1 4 5 lx 7 lx 6 2 8 v out +15v/600ma v in 4.5v to 5.5v MAX17112 u1 c2 4.7 f 10v c1 4.7 f 10v 10k c3 1 f c9 1 f c4 3.3nf c5 560pf c6 open l1 2.7 h d1 r2 47k r3 20k r4 221k c7 10 f 25v c8 10 f 25v v l ss logic input 3 9 10 shdn shdn protection resistor figure 3. application circuit using logic input at shdn designation description c1, c2 4.7f 10%, 10v x5r ceramic capacitors (0603) tdk c1608x5r1a475k c7, c8 10f 10%, 25v x5r ceramic capacitors (1210) murata grm32dr61e106k l1 2.7h 20% power inductor toko fdv0630-2r7 (27m , 4.4a) sumida cdrh5d18bhpnp-2r7m (65m , 3.9a) table 1. component list supplier phone website murata 770-436-1300 www.murata.com sumida 408-321-9660 www.sumida.com tdk 516-535-2600 www.component.tdk.com table 2. component suppliers
MAX17112 the maximum output current, input voltage, output volt- age, and switching frequency determine the inductor value. very high inductance values minimize the current ripple, and therefore, reduce the peak current, which decreases core losses in the inductor and i 2 r losses in the entire power path. however, large inductor values also require more energy storage and more turns of wire, which increase physical size and can increase i 2 r losses in the inductor. low inductance values decrease the physical size, but increase the current ripple and peak current. finding the best inductor involves choos- ing the best compromise between circuit efficiency, inductor size, and cost. the equations used here include a constant called lir, which is the ratio of the inductor peak-to-peak ripple current to the average dc inductor current at the full load current. the best trade-off between inductor size and circuit efficiency for step-up regulators generally has an lir between 0.3 and 0.5. however, depending on the ac characteristics of the inductor core material and ratio of inductor resistance to other power-path resistances, the best lir can shift up or down. if the inductor resistance is relatively high, more ripple is acceptable to reduce the number of turns required, and to increase the wire diameter. if the inductor resistance is relatively low, increasing inductance to lower the peak current can decrease losses through the power path. if extremely thin high-resistance inductors are used, as is common for lcd panel applications, the best lir can increase to between 0.5 and 1.0. once a physical inductor is chosen, higher and lower values of the inductor should be evaluated for efficien- cy improvements in typical operating regions. calculate the approximate inductor value using the typ- ical input voltage (v in ), the maximum output current (i main(eff) ), the expected efficiency ( typ ) taken from an appropriate curve in the typical operating characteristics , and an estimate of lir based on the above discussion: choose an available inductor value from an appropriate inductor family. calculate the maximum dc input cur- rent at the minimum input voltage, v in(min) , using con- servation of energy and the expected efficiency at that operating point ( min ) taken from an appropriate curve in the typical operating characteristics : calculate the ripple current at that operating point and the peak current required for the inductor: the inductor? saturation current rating and the MAX17112? lx current limit (i lim ) should exceed i peak and the inductor? dc current rating should exceed i in(dc,max) . for good efficiency, choose an inductor with less than 0.1 series resistance. considering the typical operating circuit, the maximum load current (i main(max )) is 600ma with a 15v output and a typical input voltage of 5v. choosing an lir of 0.5 and estimating 85% efficiency at this operating point: using the circuit? minimum input voltage (4.5v) and estimating 85% efficiency at this operating point: the ripple current and the peak current at that input voltage are: output capacitor selection the total output voltage ripple has two components: the capacitive ripple caused by the charging and discharg- ing of the output capacitance, and the ohmic ripple due to the capacitor? equivalent series resistance (esr): v i c vv vf ripple c main out main in main osc () ? ? ? ? ? - ? ? vv v ripple ripple c ripple esr =+ () ( ) ia a a peak =+ = 235 097 2 284 . . . i vvv ? v mhz ripple = () 45 15 45 27 15 12 09 .. .. . - 7 7a i av v a in dc max (, ) . .. . = 06 15 45 085 235 l v v vv amhz = ? ? ? ? ? ? ? ? ? ? ? ? 5 15 15 5 06 12 085 0 2 - .. . . 5 5 27 ? ? ? ? ? ? .h ii i peak in dc max ripple =+ (, ) 2 i vvv lv f ripple in min main in min main o = () () () - s sc i iv v in dc max main eff out in min min (, ) () () = l v v vv if in out main in main eff osc = ? ? ? ? ? ? ? ? ? 2 - () ? ? ? ? ? ? ? ? ? ? typ lir high-performance, step-up, dc-dc converter 10 ______________________________________________________________________________________
and: where i peak is the peak inductor current (see the inductor selection section). for ceramic capacitors, the output voltage ripple is typically dominated by v ripple(c) . the voltage rating and temperature characteristics of the output capacitor must also be considered. input capacitor selection the input capacitor (c in ) reduces the current peaks drawn from the input supply and reduces noise injec- tion into the ic. two 4.7? ceramic capacitors are used in the typical operating circuit in figure 1 because of the high source impedance seen in typical lab setups. actual applications usually have much lower source impedance since the step-up regulator often runs directly from the output of another regulated supply. typically, c in can be reduced below the values used in figure 1. ensure a low-noise supply at in by using ade- quate c in . alternatively, greater voltage variation can be tolerated on c in if in is decoupled from c in using an rc lowpass filter (see figure 1). rectifier diode selection the MAX17112 high switching frequency demands a high-speed rectifier. schottky diodes are recommended for most applications because of their fast recovery time and low forward voltage. the diode should be rated to handle the output voltage and the peak switch current. make sure that the diode? peak current rating is at least i peak calculated in the inductor selection section and that its breakdown voltage exceeds the output voltage. output voltage selection the MAX17112 operates with an adjustable output from v in to 20v. connect a resistive voltage-divider from the output (v main ) to gnd with the center tap connected to fb (see figure 1). select r3 in the 10k to 50k range. calculate r4 with the following equation: where v fb , the step-up regulator? feedback set point, is 1.24v (typ). place r3 and r4 as close as possible to the ic. loop compensation choose r comp to set the high-frequency integrator gain for fast-transient response. choose c comp to set the integrator zero to maintain loop stability. for low-esr output capacitors, use the following equa- tions to obtain stable performance and good transient response: to further optimize transient response, vary r comp in 20% steps and c comp in 50% steps while observing transient response waveforms. soft-start capacitor the soft-start capacitor should be large enough so that it does not reach final value before the output has reached regulation. calculate c ss to be: where c out is the total output capacitance including any bypass capacitor on the output bus, v out is the maximum output voltage, i inrush is the peak inrush current allowed, i out is the maximum output current during power-up, and v in is the minimum input voltage. the load must wait for the soft-start cycle to finish before drawing a significant amount of load current. the soft-start duration after which the load can begin to draw maximum load current is: pcb layout and grounding careful pcb layout is important for proper operation. use the following guidelines for good pcb layout: 1) minimize the area of high-current loops by placing the inductor, output diode, and output capacitors near the input capacitors and near the lx and gnd pins. the high-current input loop goes from the pos- itive terminal of the input capacitor to the inductor, to the ic? lx pin, out of gnd, and to the input capacitor? negative terminal. the high-current out- put loop is from the positive terminal of the input capacitor to the inductor, to the output diode (d1), to the positive terminal of the output capacitors, reconnecting between the output capacitor and input capacitor ground terminals. connect these loop components with short, wide connections. avoid using vias in the high-current paths. if vias are unavoidable, use many vias in parallel to reduce resistance and inductance. tc max ss = 24 10 5 . cc vi ss out in inrush > 21 10 6 - out 2 in out v-vv - i iv out out ? ? ? ? ? ? ? ? c vc ir comp out out out comp 10 r vv c li comp in out out out 253 rr v v main fb 43 1 = ? ? ? ? ? ? - vir ripple esr peak esr cout () ( ) MAX17112 high-performance, step-up, dc-dc converter ______________________________________________________________________________________ 11
MAX17112 high-performance, step-up, dc-dc converter maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a maxim product. no circu it patent licenses are implied. maxim reserves the right to change the circuitry and specifications without notice at any time. 12 ____________________maxim integrated products, 120 san gabriel drive, sunnyvale, ca 94086 408-737-7600 2008 maxim integrated products maxim is a registered trademark of maxim integrated products, inc. 2) create a power ground island (pgnd) consisting of the input and output capacitor grounds and gnd pins. connect all of these together with short, wide traces or a small ground plane. maximizing the width of the power ground traces improves efficien- cy and reduces output voltage ripple and noise spikes. create an analog ground plane (agnd) consisting of the feedback-divider ground connec- tion, the comp and ss capacitor ground connec- tions, and the device? exposed backside pad. connect the agnd and pgnd islands by connect- ing the gnd pins directly to the exposed backside pad. make no other connections between these separate ground planes. 3) place the feedback-voltage-divider resistors as close as possible to the feedback pin. the divider? center trace should be kept short. placing the resistors far away causes the fb trace to become an antenna that can pick up switching noise. care should be taken to avoid running the feedback trace near lx or the switching nodes in the charge pumps. 4) place in and v l pin bypass capacitors as close as possible to the device. the ground connections of the in and v l bypass capacitor should be connect- ed directly to the agnd with a wide trace. 5) minimize the length and maximize the width of the traces between the output capacitors and the load for best transient responses. 6) minimize the size of the lx node while keeping it wide and short. keep the lx node away from the feedback node and analog ground. use dc traces as a shield if necessary. refer to the MAX17112 evaluation kit for an example of proper board layout. chip information transistor count: 4624 process: bicmos package information for the latest package outline information and land patterns, go to www.maxim-ic.com/packages . package type package code document no. 10 tdfn-ep t1033+2 21-0137

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